Comparator circuit applicable to high-speed pipeline adc

ABSTRACT

The present invention provides a comparator circuit applicable to a high-speed pipeline ADC. The comparator circuit includes a switch capacitor circuit, a pre-amplification circuit, and a latch circuit. The pre-amplification circuit includes a pre-amplifier, a resistance-adjustable device, two switches. The latch circuit includes a differential static latch, a first capacitor, a second capacitor, and a third switch. The transmission rates of a sampling phase and a setup phase can be increased.

TECHNICAL FIELD

The present invention belongs to the field of semiconductor integratedcircuits, and in particular relates to a comparator circuit applicableto a high-speed pipeline ADC (Analog-to-Digital Converter).

BACKGROUND

A comparator in the form of a switch capacitor in a pipelineanalog-to-digital converter is one of its key elements. Currently commoncomparators include a comparator with a dual-capacitor architecture anda comparator with a single-capacitor architecture. The comparator withthe dual-capacitor architecture is shown in FIG. 1. In FIG. 1,corresponding switches are controlled to be turned on or off by acorresponding control signal φ1 or φ2 in FIG. 2, wherein the controlsignal φ1 is a timing of a sampling phase and the control signal φ2 is atiming of a setup phase. In the sampling phase, when the control signalφ1 is at a high level, the respective switches controlled by the controlsignal φ1 are turned on, input signals V_(IP) and V_(IN) arecorrespondingly collected to capacitors C1 and C3, and reference signalsV_(REF2) and V_(REF1) are respectively collected to capacitors C2 andC4. When the control signal φ2 reaches a rising edge, the capacitors C1to C4 need to complete charge redistribution first, thereby obtaining avoltage difference between the corresponding input signal and thereference signal. The voltage difference is then transmitted to apre-amplifier for amplification, and the amplified voltage difference islatched by a latch circuit to obtain an output result of the comparator.However, a residue amplifier in the pipeline ADC will not start to beset up until the control signal φ2 is at a high level and the outputresult is received. That is, when the control signal φ2 reaches therising edge, the residue amplifier in the pipeline MDAC needs to waitfor the output result of the comparator to be received before startingto be set up. This results in larger transmission delays (including acharge redistribution delay and a pre-amplifier transmission delay) ofthe comparator in the setup phase, thereby slowing down the conversionrate of the pipeline ADC.

In order to increase the conversion rate of the pipeline ADC, thedevelopers proposed a comparator with a single-capacitor architecture asshown in FIG. 3. In FIG. 3, corresponding switches are controlled to beturned on or off by a corresponding control signal φ1 or φ2 in FIG. 4,wherein, similarly, the control signal φ1 is a timing of a samplingphase and the control signalφ2 is a timing of a setup phase. In thesampling phase, capacitors C1 and C2 correspondingly store referencesignals V_(REF1) and V_(REF2) under the action of the control signal φ2of previous stage. Therefore, when the control signal φ1 is at a highlevel and after input signals V_(IP) and V_(IN) are correspondinglytransmitted to the capacitors C1 and C2, the capacitor C1 obtains avoltage difference between the input signal V_(IP) and the referencesignal V_(REF1), and the capacitor C2 obtains a voltage differencebetween the input signal V_(IN) and the reference signal V_(REF2). Inaddition, the two voltage differences are transmitted to thepre-amplifier for amplification, and the amplified voltage differencesare then transmitted to an input end of a latch. When the control signalφ1 reaches a falling edge, the latch transmits the amplified voltagedifferences as an output result of the comparator to the pipeline ADC.When the control signal φ2 reaches a rising edge, a residue amplifier inthe pipeline ADC can start to be set up very quickly, while thereference signals V_(REF1) and V_(REF2) are correspondingly collected tothe capacitors C1 and C2 again. Compared to the comparator with thedual-capacitor architecture, the comparator with the single-capacitorarchitecture does not have the charge redistribution delay and thepre-amplifier transmission delay, thereby increasing the transmissionrate of the comparator.

The comparator with the single-capacitor architecture has a relativelyhigher transmission rate and can increase the conversion rate of thepipeline ADC. However, according to the comparator with thesingle-capacitor architecture, in the sampling phase, a sampling networkfrom the input signals to input ends (V_(IP) and V_(LN), or V_(IN) andV_(LP)) of the latch has formed a second-order system, while a samplingnetwork of a pipeline MIDAC including only a switching resistor and asampling capacitor belongs to a first-order system, resulting in abandwidth mismatch problem when they are used together.

SUMMARY

The present invention provides a comparator circuit applicable to ahigh-speed pipeline ADC to solve a bandwidth mismatch problem that maycurrently occur when a capacitor with a single-capacitor architecture isused in conjunction with a pipeline ADC.

According to a first aspect of an embodiment of the present invention,there is provided a comparator circuit applicable to a high-speedpipeline ADC, comprising a switch capacitor circuit, a pre-amplificationcircuit and a latch circuit, wherein the pre-amplification circuitcomprises a pre-amplifier, a resistance-adjustable device, a firstswitch and a second switch; the latch circuit comprises a differentialstatic latch, a first capacitor, a second capacitor and a third switch;a first output end of the switch capacitor circuit is connected to anin-phase input end of the pre-amplifier, and a second output end of theswitch capacitor circuit is connected to an inverting input end of thepre-amplifier; an inverting output end of the pre-amplifier is connectedto a first end of the first switch; a second end of the first switch,which serves as a first output end of the pre-amplification circuit, isconnected to a positive input end of the differential static latch; anin-phase output end of the pre-amplifier is connected to a first end ofthe second switch; a second end of the second switch, which serves as asecond output end of the pre-amplification circuit, is connected to anegative input end of the differential static latch; a positive outputend of the differential static latch is connected to a positive inputend thereof through the first capacitor, and a negative output end ofthe differential static latch is connected to the negative input endthereof through the second capacitor; and the third switch is arrangedbetween the positive output end and the negative output end of thedifferential static latch.

In an optional implementation manner, the switch capacitor circuitcomprises fourth to tenth switches, a third capacitor, and a fourthcapacitor, wherein the fourth switch and the fifth switch are connectedin parallel and then connected to a first end of the third capacitor,and are configured to connect a first input signal and a first referencesignal respectively; the sixth switch and the seventh switch areconnected in parallel and then connected to a first end of the fourthcapacitor, and are respectively configured to connect a second referencesignal and a second input signal respectively; a second end of the thirdcapacitor is connected to a power supply through the eighth switch, isconnected to a second end of the fourth capacitor through the ninthswitch, and serves as the first output end of the switch capacitorcircuit; the second end of the fourth capacitor is connected to thepower supply through the tenth switch and serves as the second outputend of the switch capacitor circuit.

In another optional implementation manner, the differential static latchcomprises a first MOS transistor to a sixth MOS transistor, wherein gateelectrodes of the first MOS transistor and a second MOS transistorcorrespondingly serve as the negative input end and the positive inputend of the differential static latch, and source electrodes of the firstMOS transistor and the second MOS transistor are grounded respectively;in addition, a drain electrode of the first MOS transistor is connectedto drain electrodes of a third MOS transistor and a fifth MOS transistorrespectively; a drain electrode of the second MOS transistor isconnected to drain electrodes of a fourth MOS transistor and the sixthMOS transistor respectively; source electrodes of the third MOStransistor and the fourth MOS transistor are grounded respectively andgate electrodes thereof are connected to drain electrodes of each otherrespectively; source electrodes of the fifth MOS transistor and thesixth MOS transistor are connected to the power supply and the gateelectrodes thereof are connected to drain electrodes of each otherrespectively; the drain electrode of the fourth MOS transistor serves asthe negative output end of the differential static latch; and the drainelectrode of the third MOS transistor serves as the positive output endof the differential static latch.

In another optional implementation manner, the third switch serves as aseventh MOS transistor; a source electrode of the seventh MOS transistoris connected to the positive output end of the differential staticlatch, a drain electrode of the seventh MOS transistor is connected tothe negative output end of the differential static latch, and a gateelectrode of the seventh MOS transistor is connected to thecorresponding control signal.

In yet another optional implementation manner, by reducing the size ofan input tube in the pre-amplifier, a sampling network of the comparatorcircuit is reduced to a first-order system to match the first-orderhigh-speed pipeline ADC.

In another optional implementation manner, a signal transmission rate ofa sampling phase is adjusted by adjusting a resistance value of theresistance-adjustable device; the smaller the resistance value of theresistance-adjustable device is, and correspondingly the larger thesignal transmission rate of the sampling phase is.

In another optional implementation manner, the transmission rate of thesampling phase of the comparator circuit is increased by increasing anoutput resistance of the latch circuit.

In another optional implementation manner, an output resistance of thelatch circuit is adjusted by adjusting the amplitude of thecorresponding control signal applied to the gate electrode of theseventh MOS transistor, thereby adjusting the transmission rate of thesampling phase.

In another optional implementation manner, the first switch, the secondswitch, the third switch, the fourth switch and the seventh switch arecontrolled to be turned on or off by a control signal φ1; the fifthswitch, the sixth switch, the eighth switch, the ninth switch and thetenth switch are controlled to be turned on or off by a control signalφ2; and the control signal φ1 and the control signal φ2 are two-phasenon-overlapping clock signals.

In another optional implementation manner, the resistance-adjustabledevice comprises an adjustable resistor, or an MOS transistor with anadjustable on-voltage at a gate electrode.

The present invention has the following beneficial effects:

According to the comparator circuit of the present invention, theresistance-adjustable device is additionally arranged in thepre-amplification circuit. By adjusting the resistance value of theresistance-adjustable device, the transmission rate of the samplingphase of the comparator can be adjusted on the one hand, and theamplitude of an output signal of the pre-amplifier can be clamped on theother hand, thereby reducing the kickback noise coupled to the inputend. The output resistance of the latch circuit can be increased byadditionally arranging the first capacitor and the second capacitor inthe latch circuit and using the differential static latch as the latchin the latch circuit, thereby increasing the transmission rate of thesampling phase of the comparator circuit. The resistance value of theresistance-adjustable device of the present invention is adjustable, sothe transmission rate of the sampling phase of the comparator circuitcan be adjusted. In addition, when the third switch in the latch circuitserves as the seventh MOS transistor, the amplitude of the outputresistance of the latch circuit is adjusted by adjusting the amplitudeof the control signal on the gate electrode of the seventh MOStransistor. Therefore, the transmission rate of the sampling phase ofthe comparator may further be adjusted. Accordingly, it is possible forthe present invention to achieve the match between the transmission rateof the comparator circuit and an operating rate of the high-speedpipeline MDAC.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a circuit diagram of a comparator with a dual-capacitorarchitecture;

FIG. 2 is an operating timing diagram of the comparator with thedual-capacitor architecture;

FIG. 3 is a circuit diagram of a comparator with a single-capacitorarchitecture;

FIG. 4 is an operating timing diagram of the comparator with thesingle-capacitor architecture;

FIG. 5 is a circuit diagram of an embodiment of a comparator circuitapplicable to a high-speed pipeline ADC according to the presentinvention;

FIG. 6 is a circuit diagram of an embodiment of a latch circuit in FIG.5;

FIG. 7 is an operating timing diagram of the comparator circuitapplicable to the high-speed pipeline ADC according to the presentinvention;

FIG. 8 is a single-ended small-signal equivalent circuit diagramaccording to the present invention; and

FIG. 9 is a schematic view showing a change trend of a pole over apositive feedback strength according to the present invention.

DETAILED DESCRIPTION

In order to make those skilled in the art understand the technicalsolutions in embodiments of the present invention better and make saidobjects, features and advantages of the embodiments of the presentinvention more apparent, the technical solutions in the embodiment ofthe present invention will be described further in detail in conjunctionwith the accompanying drawings.

In the description of the present invention, unless otherwise specifiedand limited, it should be noted that the term “connected” needs to bebroadly understood, for example, connection may be mechanicalconnection, electrical connection, communication of inner parts of twoelements, direct connection, or indirect connection via anintermediation. Those ordinary skilled in the art can understand thespecific meaning of the above terms in accordance with specificconditions.

In order to solve the problem of bandwidth mismatch between a comparatorwith a single-capacitor architecture and a pipeline MDAC, the comparatorwith the single-capacitor architecture can be designed in a reducedorder. The Applicants, upon researches, have found that, by reducing thesize of an input transistor in the pre-amplifier, the input transistorhas a very small parasitic capacitance, such that a sampling network ofa comparator circuit can be reduced to a first-order system to match ahigh-speed pipeline MADC of the first-order system. Although the problemof system bandwidth mismatch between the comparator and the high-speedpipeline ADC can be solved accordingly, since a load of the pipelineMADC is relatively fixed, and the size of an input transistor of thelatch cannot be reduced (if it is reduced, the corresponding driverstage needs to be increased, thereby increasing the transmission delay),in the cases where the size of a pre-amplifier is limited and the loadis correspondingly fixed, the transmission rate of the sampling networkof the comparator with the single-capacitor architecture is relativelylower, and the pre-amplifier can only use a single-stage amplifier,accompanied with a poor insulation effect and relatively larger kickbacknoise. Therefore, it is also necessary to solve the problem that thetransmission rate of the sampling network is reduced while thecomparator with the single-capacitor architecture is designed in areduced order.

FIG. 5 is a circuit diagram of an embodiment of a comparator circuitapplicable to a high-speed pipeline ADC according to the presentinvention. The comparator circuit applicable to the high-speed pipelineADC may comprise a switch capacitor circuit 110, a pre-amplifier circuit120, and a latch circuit 130. The pre-amplifier circuit 120 may comprisea pre-amplifier A1, a resistance-adjustable device R1, a first switchS1, and a second switch S2. The latch circuit 130 may comprise adifferential static latch A2, a first capacitor C1, a second capacitorC2, and a third switch S3. A first output end Vp of the switch capacitorcircuit 110 is connected to an in-phase input end of the pre-amplifierA1, and a second output end Vn of the switch capacitor circuit 110 isconnected to an inverting input end of the pre-amplifier A1. Aninverting output end of the pre-amplifier A1 is connected to a first endof the first switch S1. A second end of the first switch S1, whichserves as a first output end V_(LN) of the pre-amplification circuit120, is connected to a positive input end of the differential staticlatch A2. An in-phase output end of the pre-amplifier A1 is connected toa first end of the second switch S2. A second end of the second switchS2, which serves as a second output end V_(LP) of the pre-amplificationcircuit, is connected to a negative input end of the differential staticlatch A2. A positive output end of the differential static latch A2 isconnected to the positive input end thereof through the first capacitorC1. A negative output end of the differential static latch A2 isconnected to the negative input end thereof through the second capacitorC2. In addition, the third switch S3 is arranged between the positiveoutput end and the negative output end of the differential static latchA2. The positive output end of the differential static latch A2 servesas a first output end V_(ON) of the latch circuit 130, and the negativeoutput end of the differential static latch A2 serves as a second outputend V_(OP) of the latch circuit 130. The first output end V_(ON) and thesecond output end V_(OP) are connected to corresponding ends of thepipeline ADC. The resistance-adjustable device R1 may be an adjustableresistor, or an MOS having an adjustable on-voltage at a gate electrode.The on-resistance of the MOS transistor can be adjusted by adjusting theamplitude of the on-voltage of the gate electrode of the MOS(Metal-Oxide-Semiconductor Field-Effect Transistor), thereby achievingresistance value adjustment. The higher the on-voltage of the gateelectrode of the MOS transistor is, and correspondingly the smaller theon-resistance of the MOS transistor is.

The switch capacitor circuit comprises a fourth switch S4 to a tenthswitch S10, a third capacitor C3, and a fourth capacitor C4, wherein thefourth switch S4 and the fifth switch S5 are connected in parallel andthen connected to a first end of the third capacitor C3, and areconfigured to connect a first input signal V_(IP) and a first referencesignal V_(REF1) respectively. The sixth switch S6 and the seventh switchS7 are connected in parallel and then connected to a first end of thefourth capacitor C4, and are configured to connect a second referencesignal V_(REF2) and a second input signal V_(IN) respectively. A secondend of the third capacitor C3 is connected to a power supply V_(CM)through the eighth switch S8, is connected to a second end of the fourthcapacitor C4 through the ninth switch S9, and serves as a first outputend Vp of the switch capacitor circuit 110. A second end of the fourthcapacitor C4 is connected to the power supply V_(CM) through the tenthswitch S10 and serves as a second output end Vn of the switch capacitorcircuit 110.

In addition, as shown in FIG. 6, the differential static latch A2 maycomprise a first MOS transistor M1 to a sixth MOS transistor M6, whereingate electrodes of the first MOS transistor M1 and the second MOStransistor M2 correspondingly serve as the negative input end and thepositive input end (which are correspondingly connected to the secondoutput end V_(LP) and the first output end V_(LN) of thepre-amplification circuit 120) of the differential static latch A1, andsource electrodes of the first MOS transistor M1 and the second MOStransistor M2 are grounded respectively. In addition, a drain electrodeof the first MOS transistor M1 is connected to drain electrodes of thethird MOS transistor M3 and the fifth MOS transistor M5 respectively. Adrain electrode of the second MOS transistor M2 is connected to drainelectrodes of the fourth MOS transistor M4 and the sixth MOS transistorM6 respectively. Source electrodes of the third MOS transistor M3 andthe fourth MOS transistor M4 are grounded respectively and gateelectrodes thereof are connected to drain electrodes of each otherrespectively. Source electrodes of the fifth MOS transistor M5 and thesixth MOS transistor M6 are connected to the power supply V_(CM) and thegate electrodes thereof are connected to drain electrodes of each other.The drain electrode of the fourth MOS transistor M4 serves as thenegative output end (corresponding to the second output end V_(OP) ofthe latch circuit 130) of the differential static latch A2. The drainelectrode of the third MOS transistor M3 serves as the positive outputend (corresponding to the first output end V_(ON) of the latch circuit130) of the differential static latch A2. In the present embodiment, thethird switch S3 may serve as a seventh MOS transistor M7 in FIG. 6. Asource electrode of the seventh MOS transistor M7 is connected to thepositive output end of the differential static latch, a drain electrodeof the seventh MOS transistor M7 is connected to the negative output endof the differential static latch, and the gate electrode of the seventhMOS transistor M7 is connected to the corresponding control signal φ1.

As shown in FIG. 5, the first switch S1, the second switch S2, the thirdswitch S3, the fourth switch S4 and the seventh switch S7 are controlledto be turned on or off by a control signal φ1. The fifth switch S5, thesixth switch S6, the eighth switch S8, the ninth switch S9 and the tenthswitch S10 are controlled to be turned on or off by a control signal φ2.The control signal φ1 and the control signal φ2 are two-phasenon-overlapping clock signals, and the operating timing diagrams of thecontrol signal φ1 and the control signal φ2 are as shown in FIG. 7. Thecontrol signal φ1 is a timing of a sampling phase and the control signalφ2 is a timing of a setup phase. In the sampling phase, the thirdcapacitor C3 and the fourth capacitor C4 correspondingly store referencesignals V_(REF1) and V_(REF2) under the action of the control signal φ2of previous stage. Therefore, when the control signal φ1 is at a highlevel and after input signals V_(IP) and V_(IN) are correspondinglytransmitted to the capacitors C1 and C2, the capacitor C1 obtains avoltage difference between the input signal V_(IP) and the referencesignal V_(REF1), and the capacitor C2 obtains a voltage differencebetween the input signal V_(IN) and the reference signal V_(REF2). Inaddition, the two voltage differences are transmitted to thepre-amplifier for amplification, and the amplified voltage differencesare then transmitted to an input end of the latch. When the controlsignal φ1 reaches a falling edge, the latch transmits the amplifiedvoltage differences as an output result of the comparator to thepipeline ADC. When the control signal φ2 reaches a rising edge, aresidue amplifier in the pipeline ADC can start to be set up, while thereference signals V_(REF1) and V_(REF2) are correspondingly collected tothe capacitors C1 and C2 again.

According to the comparator circuit, the resistance-adjustable device isadditionally arranged in the pre-amplification circuit. By adjusting theresistance value of the resistance-adjustable device, the transmissionrate (i.e., the transmission rate of the sampling phase) of thepre-amplification circuit can be adjusted on the one hand, and theamplitude of an output signal of the pre-amplifier can be clamped on theother hand, thereby reducing the kickback noise coupled to the inputend. The smaller the resistance value of the resistance-adjustabledevice is, and correspondingly the larger the signal transmission rateof the sampling phase is.

The first capacitor C1 and the second capacitor C2 which are configuredfor positive feedback are additionally arranged in the latch circuit.The positive feedback can adjust a zero-pole of a sampling circuit. Asthe feedback strength increases, a real pole can be modulated into acomplex pole. However, the positive feedback strength is determined bysmall-signal gains of the first capacitor C1 and the second capacitorC2. Therefore, the latch in the latch circuit must be a static latch toensure that a certain gain can also be provided in the sampling phase. Asingle-ended small-signal model of the latch is as shown in FIG. 8. Asmall-signal gain of the latch determines the feedback strength. Achange curve of a pole over the output resistance of the latch circuitis as shown in FIG. 9 (the arrow direction indicates a direction inwhich the output resistance increases). When the output resistance isrelatively small and the feedback gain is very low, two real poles whichare far apart are obtained. As the output resistance increases, thepoles gradually approach each other and become two complex poles whichmove towards the right half plane. As the complex poles move towards theright half plane, the damping coefficient becomes smaller and smaller,which causes the phase change on the phase frequency response to becomeslower and slower. Correspondingly, in the time domain, the transmissiondelay will be smaller, thereby achieving the effect of high-speedtransmission. When the third switch S3 is the seventh MOS transistor M7,the on-resistance of the seventh MOS transistor can be adjusted byadjusting the amplitude of the control signal φ1 applied to the gateelectrode of the seventh MOS transistor, thereby adjusting the outputresistance of the latch circuit and thus adjusting the transmission rateof the sampling phase of the comparator circuit.

As can be seen from the above embodiments, the resistance-adjustabledevice is additionally arranged in the pre-amplification circuit. Byadjusting the resistance value of the resistance-adjustable device, thetransmission rate of the sampling phase of the comparator can beadjusted on the one hand, and the amplitude of the output signal of thepre-amplifier can be clamped on the other hand, thereby reducing thekickback noise coupled to the input end. The output resistance of thelatch circuit can be increased by additionally arranging the firstcapacitor and the second capacitor in the latch circuit and using thedifferential static latch as the latch in the latch circuit, therebyincreasing the transmission rate of the sampling phase of the comparatorcircuit. The resistance value of the resistance-adjustable device of thepresent invention is adjustable, so the transmission rate of thesampling phase of the comparator circuit can be adjusted. In addition,when the third switch in the latch circuit serves as the seventh MOStransistor, the amplitude of the output resistance of the latch circuitis adjusted by adjusting the amplitude of the control signal at the gateelectrode of the seventh MOS transistor. Therefore, the transmissionrate of the sampling phase of the comparator may further adjusted.Accordingly, it is possible for the present invention to achieve thematch between the transmission rate of the comparator circuit and anoperating rate of the high-speed pipeline MDAC.

Upon consideration of the description and practice of the presentinvention disclosed herein, other embodiments of the present inventionwill be readily apparent to those skilled in the art. The presentapplication is intended to cover any variations, uses, or adaptations ofthe present invention, which conform to general principles of thepresent invention and include the common sense or conventional technicalmeans in the art that is not disclosed in the present invention. Thedescription and embodiments are merely considered as exemplary. The truescope and spirit of the present invention are indicated by the followingclaims.

It should be understood that the present invention is not limited to theabove-described precise structures shown in the drawings, and variousmodifications and changes can be made without departing from the scopethereof. The scope of the present invention is limited only by appendedclaims.

1: A comparator circuit applicable to a high-speed pipeline ADC(Analog-to-Digital Converter), comprising a switch capacitor circuit, apre-amplification circuit and a latch circuit, wherein thepre-amplification circuit comprises a pre-amplifier, aresistance-adjustable device, a first switch and a second switch; thelatch circuit comprises a differential static latch, a first capacitor,a second capacitor and a third switch; a first output end of the switchcapacitor circuit is connected to an in-phase input end of thepre-amplifier, and a second output end of the switch capacitor circuitis connected to an inverting input end of the pre-amplifier; aninverting output end of the pre-amplifier is connected to a first end ofthe first switch; a second end of the first switch, which serves as afirst output end of the pre-amplification circuit, is connected to apositive input end of the differential static latch; an in-phase outputend of the pre-amplifier is connected to a first end of the secondswitch; a second end of the second switch, which serves as a secondoutput end of the pre-amplification circuit, is connected to a negativeinput end of the differential static latch; a positive output end of thedifferential static latch is connected to the positive input end thereofthrough the first capacitor, and a negative output end of thedifferential static latch is connected to the negative input end thereofthrough the second capacitor; and the third switch is arranged betweenthe positive output end and the negative output end of the differentialstatic latch. 2: The comparator circuit applicable to the high-speedpipeline ADC according to claim 1, wherein the switch capacitor circuitcomprises fourth to tenth switches, a third capacitor, and a fourthcapacitor, wherein the fourth switch and the fifth switch are connectedin parallel and then connected to a first end of the third capacitor,and are configured to connect a first input signal and a first referencesignal respectively; the sixth switch and the seventh switch areconnected in parallel and then connected to a first end of the fourthcapacitor, and are configured to connect a second reference signal and asecond input signal respectively; a second end of the third capacitor isconnected to a power supply through the eighth switch, is connected to asecond end of the fourth capacitor through the ninth switch, and servesas the first output end of the switch capacitor circuit; the second endof the fourth capacitor is connected to the power supply through thetenth switch and serves as the second output end of the switch capacitorcircuit. 3: The comparator circuit applicable to the high-speed pipelineADC according to claim 1, wherein the differential static latchcomprises a first MOS transistor to a sixth MOS transistor, wherein gateelectrodes of the first MOS transistor and a second MOS transistorcorrespondingly serve as the negative input end and the positive inputend of the differential static latch, and source electrodes of the firstMOS transistor and the second MOS transistor are grounded respectively;in addition, a drain electrode of the first MOS transistor is connectedto drain electrodes of a third MOS transistor and a fifth MOS transistorrespectively; a drain electrode of the second MOS transistor isconnected to drain electrodes of a fourth MOS transistor and the sixthMOS transistor respectively; source electrodes of the third MOStransistor and the fourth MOS transistor are grounded respectively andgate electrodes thereof are connected to drain electrodes of each otherrespectively; source electrodes of the fifth MOS transistor and thesixth MOS transistor are connected to the power supply and the gateelectrodes thereof are connected to drain electrodes of each otherrespectively; the drain electrode of the fourth MOS transistor serves asthe negative output end of the differential static latch; and the drainelectrode of the third MOS transistor serves as the positive output endof the differential static latch. 4: The comparator circuit applicableto the high-speed pipeline ADC according to claim 1, wherein the thirdswitch serves as a seventh MOS transistor; a source electrode of theseventh MOS transistor is connected to the positive output end of thedifferential static latch, a drain electrode of the seventh MOStransistor is connected to the negative output end of the differentialstatic latch, and a gate electrode of the seventh MOS transistor isconnected to the corresponding control signal. 5: The comparator circuitapplicable to the high-speed pipeline ADC according to claim 1, wherein,by reducing the size of an input tube in the pre-amplifier, a samplingnetwork of the comparator circuit is reduced to a first-order system tomatch a first-order sampling network of the high-speed pipeline MDAC. 6:The comparator circuit applicable to the high-speed pipeline ADCaccording to claim 5, wherein a signal transmission rate of a samplingphase is adjusted by adjusting a resistance value of theresistance-adjustable device; the smaller the resistance value of theresistance-adjustable device is, and correspondingly the larger thesignal transmission rate of the sampling phase is. 7: The comparatorcircuit applicable to the high-speed pipeline ADC according to claim 1,wherein the transmission rate of the sampling phase of the comparatorcircuit is increased by increasing an output resistance of the latchcircuit. 8: The comparator circuit applicable to the high-speed pipelineADC according to claim 4, wherein an output resistance of the latchcircuit is adjusted by adjusting the amplitude of the correspondingcontrol signal applied to the gate electrode of the seventh MOStransistor, thereby adjusting the transmission rate of the samplingphase. 9: The comparator circuit applicable to the high-speed pipelineADC according to claim 2, wherein the first switch, the second switch,the third switch, the fourth switch and the seventh switch arecontrolled to be turned on or off by a control signal φ1; the fifthswitch, the sixth switch, the eighth switch, the ninth switch and thetenth switch are controlled to be turned on or off by a control signalφ2; and the control signal φ1 and the control signal φ2 are two-phasenon-overlapping clock signals. 10: The comparator circuit applicable tothe high-speed pipeline ADC according to claim 1, wherein theresistance-adjustable device comprises an adjustable resistor, or an MOStransistor with an adjustable on-voltage at a gate electrode. 11: Thecomparator circuit applicable to the high-speed pipeline ADC accordingto claim 3, wherein the first switch, the second switch, the thirdswitch, the fourth switch and the seventh switch are controlled to beturned on or off by a control signal φ1; the fifth switch, the sixthswitch, the eighth switch, the ninth switch and the tenth switch arecontrolled to be turned on or off by a control signal φ2; and thecontrol signal φ1 and the control signal φ2 are two-phasenon-overlapping clock signals. 12: The comparator circuit applicable tothe high-speed pipeline ADC according to claim 4, wherein the firstswitch, the second switch, the third switch, the fourth switch and theseventh switch are controlled to be turned on or off by a control signalφ1; the fifth switch, the sixth switch, the eighth switch, the ninthswitch and the tenth switch are controlled to be turned on or off by acontrol signal φ2; and the control signal φ1 and the control signal φ2are two-phase non-overlapping clock signals. 13: The comparator circuitapplicable to the high-speed pipeline ADC according to claim 5, whereinthe first switch, the second switch, the third switch, the fourth switchand the seventh switch are controlled to be turned on or off by acontrol signal φ1; the fifth switch, the sixth switch, the eighthswitch, the ninth switch and the tenth switch are controlled to beturned on or off by a control signal φ2; and the control signal φ1 andthe control signal φ2 are two-phase non-overlapping clock signals. 14:The comparator circuit applicable to the high-speed pipeline ADCaccording to claim 6, wherein the first switch, the second switch, thethird switch, the fourth switch and the seventh switch are controlled tobe turned on or off by a control signal φ1; the fifth switch, the sixthswitch, the eighth switch, the ninth switch and the tenth switch arecontrolled to be turned on or off by a control signal φ2; and thecontrol signal φ1 and the control signal φ2 are two-phasenon-overlapping clock signals. 15: The comparator circuit applicable tothe high-speed pipeline ADC according to claim 7, wherein the firstswitch, the second switch, the third switch, the fourth switch and theseventh switch are controlled to be turned on or off by a control signalφ1; the fifth switch, the sixth switch, the eighth switch, the ninthswitch and the tenth switch are controlled to be turned on or off by acontrol signal φ2; and the control signal φ1 and the control signal φ2are two-phase non-overlapping clock signals. 16: The comparator circuitapplicable to the high-speed pipeline ADC according to claim 8, whereinthe first switch, the second switch, the third switch, the fourth switchand the seventh switch are controlled to be turned on or off by acontrol signal φ1; the fifth switch, the sixth switch, the eighthswitch, the ninth switch and the tenth switch are controlled to beturned on or off by a control signal φ2; and the control signal φ1 andthe control signal φ2 are two-phase non-overlapping clock signals.